11 research outputs found

    Stator-Flux-Oriented Vector Control of Synchronous Reluctance Machines With Maximized Efficiency

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    Direct Flux Field Oriented Control of IPM Drives with Variable DC-Link in the Field-Weakening Region

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    This paper presents the direct flux control of an interior permanent-magnet (IPM) motor drive in the field-weakening region. The output torque is regulated by the coordinated control of the stator flux amplitude and the current component in quadrature with the flux, and it is implemented in the stator flux reference frame. The control system guarantees maximum torque production taking into account voltage and current limits, in particular in case of large dc-link variations. The field-oriented control does not necessarily require an accurate magnetic model of the IPM motor, and it is able to exploit the full inverter voltage at different dc-link levels with no additional voltage control loop. The feasibility of the proposed control method is investigated in discrete-time simulation, then tested on a laboratory rig, and finally implemented on board of an electric scooter prototype. The motor under test is an IPM permanent-magnet-assisted synchronous reluctance machine, with high-saliency and limited permanent-magnet flu

    Optimal Efficiency Control of Synchronous Reluctance Motors-based ANN Considering Cross Magnetic Saturation and Iron Loss

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    This paper presents a new idea by using the Artificial Neural Networks (ANNs) for estimating the parameters of the machine which achieving the maximum efficiency of the Synchronous Reluctance Motor (SynRM). This model take into consideration the magnetic saturation, cross-coupling and iron loss. With Finite Element Analysis (FEA), the characteristics of the SynRM including inductances and iron loss resistance are determined. Because of the non-linear characteristics, an ANN trained off-line, is then proposed to obtain the d-q inductances and iron loss resistance from Id,Iq currents and the speed. After learning process, an analytical expression of the optimal currents is given thanks to Lagrange optimization. Therefore, the optimal currents will be obtained online in real time. This method can be achieved with maximum efficiency and high-precision torque control. Simulation and experimental results are presented to confirm the validity of the proposed method

    FIELD ORIENTED CONTROL OF IPM DRIVES FOR FLUX WEAKENING APPLICATIONS

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    Interior Permanent Magnet (IPM) drives are adapted to flux-weakening, then to constant power operation over a wide speed range. Most of the control strategies for IPM motor drives are based on the control of the current vector. Flux-weakening is obtained by proper current references, that are calculated according to the magnetic model of the motor. This approach needs the accurate characterization of the motor and it is sensitive to the inaccuracy and the variation of the model parameters. Moreover, in the case of a variable dc-link, an additional voltage loop is necessary to correct the current references values at different dc-link voltage levels. The direct control of the flux vector, in the stator flux oriented frame, is proposed here, with the aim of obtaining the constant voltage operation of the IPM motor drive in the flux weakening range by means of a very simple control algorithm. The proposed direct flux control is tested on an IPM motor drive designed for traction. The exploitation of the maximum torque in all the operating speed range is demonstrated. The control is also capable to adapt its flux and current set-points to different dc-link voltage levels with no need of additional voltage regulators. Discrete-time simulation and experimental results are presented and compared showing good accordance

    Six-Step Operation of Three-Phase PMSM Based on Flux Vector Prediction

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    ํ•™์œ„๋…ผ๋ฌธ(๋ฐ•์‚ฌ) -- ์„œ์šธ๋Œ€ํ•™๊ต๋Œ€ํ•™์› : ๊ณต๊ณผ๋Œ€ํ•™ ์ „๊ธฐยท์ •๋ณด๊ณตํ•™๋ถ€, 2023. 2. ์„ค์Šน๊ธฐ.3์ƒ ์ธ๋ฒ„ํ„ฐ์˜ ์‹์Šค-์Šคํ… ์šด์ „(Six-step operation)์€ ์ „์•• ์œก๊ฐํ˜•์˜ ๊ผญ์ง“์  ๋ฒกํ„ฐ๋งŒ์„ ์ด์šฉํ•˜์—ฌ ์ง๋ฅ˜๋‹จ ์ „์•• ์ด์šฉ๋ฅ ์„ ์ตœ๋Œ€ํ™”ํ•˜๋Š” ์šด์ „ ๊ธฐ๋ฒ•์ด๋‹ค. ์‹์Šค-์Šคํ… ์šด์ „์„ ํ†ตํ•˜์—ฌ, ์ฃผ์–ด์ง„ ์ง๋ฅ˜๋‹จ ์ „์•• ์กฐ๊ฑด ํ•˜์—์„œ ์ „๋™๊ธฐ์˜ ๊ฐ€์šฉ ํ† ํฌ๋ฅผ ์ตœ๋Œ€ํ™” ํ•  ์ˆ˜ ์žˆ๋‹ค. ๋˜ํ•œ ํŽ„์Šคํญ ๋ณ€์กฐ(Pulse-width modulation, PWM)์™€ ๋น„๊ตํ•˜์—ฌ, ์ธ๋ฒ„ํ„ฐ์˜ ์Šค์œ„์นญ ์†์‹ค์ด ํ˜„์ €ํžˆ ์ค„์–ด๋“ ๋‹ค๋Š” ์žฅ์ ์ด ์žˆ๋‹ค. ์ด๋Ÿฌํ•œ ์ด์œ ๋กœ ๋†’์€ ์ถœ๋ ฅ ํ† ํฌ ๋ฐ ์ธ๋ฒ„ํ„ฐ ํšจ์œจ์„ ์–ป์„ ์ˆ˜ ์žˆ๋Š” ์‹์Šค-์Šคํ… ์šด์ „์— ๋Œ€ํ•œ ์—ฐ๊ตฌ๊ฐ€ ํ™œ๋ฐœํ•˜๊ฒŒ ์ด๋ฃจ์–ด์ง€๊ณ  ์žˆ๋‹ค. ์‹์Šค-์Šคํ… ์šด์ „์‹œ ์ „์••์˜ ํฌ๊ธฐ๋Š” ์ตœ๋Œ€ํ™”๋œ ์ƒํƒœ์ด๋ฏ€๋กœ, ์ถœ๋ ฅ ์ „์••์˜ ์œ„์ƒ๋งŒ์ด ์ •์ƒ์ƒํƒœ ์ž์œ ๋„๋กœ ๋‚จ๊ฒŒ ๋œ๋‹ค. ๋‹ค์ˆ˜์˜ ์„ ํ–‰ ์—ฐ๊ตฌ๋“ค์€ ์ „์••๊ฐ์— ์ดˆ์ ์„ ๋งž์ถ”์–ด ๊ธฐ๋ณธํŒŒ ์ „์••๊ฐ์˜ ๋ณ€ํ™”๋ถ„์„ ์ž…๋ ฅ์œผ๋กœ ๊ฐ€์ง€๋Š” ์„ ํ˜• ์‹œ์Šคํ…œ์œผ๋กœ ์˜๊ตฌ์ž์„ ๋™๊ธฐ ์ „๋™๊ธฐ(Permanent-magnet synchronous motor, PMSM)์˜ ์‹์Šค-์Šคํ… ์šด์ „์„ ๋ชจ๋ธ๋งํ•˜๊ณ , ๋ชจ๋ธ๋ง์— ๊ธฐ๋ฐ˜ํ•˜์—ฌ ์ฃผํŒŒ์ˆ˜ ์˜์—ญ(Frequency domain) ๋ถ„์„์„ ํ†ตํ•ด ์ œ์–ด๊ธฐ๋ฅผ ์„ค๊ณ„ํ•˜์˜€๋‹ค. ํ•˜์ง€๋งŒ ํ•ด๋‹น ๋ชจ๋ธ๋ง์€ ํ‰ํ˜•์  ๊ทผ๋ฐฉ์˜ ์†Œ์‹ ํ˜ธ ๋ถ„์„์„ ๋ฐ”ํƒ•์œผ๋กœ ์ˆ˜๋ฆฝ๋˜๋ฏ€๋กœ, ๋Œ€์‹ ํ˜ธ์— ๋Œ€ํ•œ ์ •ํ™•์„ฑ์ด ๋ณด์žฅ๋˜์ง€ ์•Š๋Š”๋‹ค. ๋˜ํ•œ ์ฃผํŒŒ์ˆ˜ ์˜์—ญ์—์„œ์˜ ๋ถ„์„์€ ์ถœ๋ ฅ ์ „์••์˜ ๊ธฐ๋ณธํŒŒ ์„ฑ๋ถ„์—๋งŒ ์ดˆ์ ์„ ๋งž์ถ”๊ธฐ ๋•Œ๋ฌธ์—, ์‹์Šค-์Šคํ… ์šด์ „์˜ ๊ณ ์กฐํŒŒ ์ „์•• ์„ฑ๋ถ„์ด ๋™ํŠน์„ฑ์— ๋ผ์น˜๋Š” ์˜ํ–ฅ์ด ๊ณ ๋ ค๋˜์ง€ ์•Š๋Š”๋‹ค. ์ด๋Ÿฌํ•œ ๋ชจ๋ธ๋ง ์˜ค์ฐจ๋Š” ์‹์Šค-์Šคํ… ์šด์ „์˜ ๋™ํŠน์„ฑ ํ–ฅ์ƒ์— ์žˆ์–ด ์ œ์•ฝ ์‚ฌํ•ญ์œผ๋กœ ์ž‘์šฉํ•œ๋‹ค. ๋ณธ ๋…ผ๋ฌธ์€ PMSM ์‹์Šค-์Šคํ… ์šด์ „์˜ ๋™ํŠน์„ฑ ํ–ฅ์ƒ ๋ฐฉ๋ฒ•์— ๋Œ€ํ•˜์—ฌ ์—ฐ๊ตฌํ•œ๋‹ค. ํšŒ์ „์ž ๊ธฐ์ค€ ์ขŒํ‘œ๊ณ„ ์ƒ์—์„œ ์‹์Šค-์Šคํ… ์šด์ „์˜ ์ˆœ์‹œ ์ „์••์€ ํšŒ์ „์ž์˜ ๋ฐ˜๋Œ€ ๋ฐฉํ–ฅ์œผ๋กœ ํšŒ์ „ํ•˜๋Š” ํšจ๊ณผ๋ฅผ ์ง€๋‹Œ๋‹ค. ๋ณธ ๋…ผ๋ฌธ์—์„œ๋Š” ์ˆœ์‹œ ์ „์••์˜ ํšŒ์ „ ํšจ๊ณผ๋ฅผ ๋ฐ˜์˜ํ•˜๊ธฐ ์œ„ํ•˜์—ฌ ์‹œ๊ฐ„ ์˜์—ญ(Time domain)์—์„œ ๋ถ„์„์„ ์ง„ํ–‰ํ•œ๋‹ค. ํšŒ์ „์ž ๊ธฐ์ค€ ์ขŒํ‘œ๊ณ„ ์ƒ์—์„œ ์ „์•• ์ธ๊ฐ€ ์‹œ๊ฐ„์— ๋”ฐ๋ฅธ ์ˆœ์‹œ ์ž์† ๊ถค์ ์„ ์ˆ˜์‹ํ™”ํ•˜๊ณ , ์ด๋ฅผ ๋ฐ”ํƒ•์œผ๋กœ PMSM ์‹์Šค-์Šคํ… ์šด์ „์˜ ์‹œ๊ฐ„-์ตœ์ (Time-optimal) ์ ˆํ™˜ ๋ฐฉ๋ฒ•์„ ์œ ๋„ํ•œ๋‹ค. ํšŒ์ „์ž ๊ธฐ์ค€ ์ขŒํ‘œ๊ณ„ ์ƒ์—์„œ ์ž์†์˜ ์‹œ๊ฐ„-์ตœ์  ๊ฒฝ๋กœ๋Š” ๋ชฉํ‘œ ์šด์ „์ ์„ ํฌ๊ฒŒ ์šฐํšŒํ•˜๋Š” ํ˜•ํƒœ๋กœ ๋‚˜ํƒ€๋‚œ๋‹ค. ์ด๋Ÿฌํ•œ ๊ฒฝ๋กœ๋Š” ํšŒ์ „์ž ๊ธฐ์ค€ ์ขŒํ‘œ๊ณ„์—์„œ ์„ค๊ณ„๋œ ์„ ํ˜• ์ œ์–ด๊ธฐ๋ฅผ ํ†ตํ•ด ๊ตฌํ˜„ํ•˜๊ธฐ ์–ด๋ ต๊ณ , ๊ฐœ๋ฃจํ”„ ํ˜•ํƒœ๋ฅผ ์ทจํ•ด์•ผ ํ•œ๋‹ค๋Š” ๋ฌธ์ œ์ ์ด ์กด์žฌํ•œ๋‹ค. ๋ฐ˜๋ฉด, ์ •์ง€ ์ขŒํ‘œ๊ณ„ ์ƒ์—์„œ ์ž์†์˜ ์‹œ๊ฐ„-์ตœ์  ๊ฒฝ๋กœ๋Š” ์ถœ๋ ฅ ํ† ํฌ ์ฆ๊ฐ€ ์ƒํ™ฉ์—์„  ์ง€๋ฆ„๊ธธ๋กœ, ๊ฐ์†Œ ์ƒํ™ฉ์—์„  ์šฐํšŒ๋กœ๋กœ ๋‚˜ํƒ€๋‚œ๋‹ค. ๋ณธ ๋…ผ๋ฌธ์—์„œ๋Š” ์ •์ง€ ์ขŒํ‘œ๊ณ„ ์ž์† ๊ถค์ ์— ๋Œ€ํ•œ ๊ณ ์ฐฐ์„ ๋ฐ”ํƒ•์œผ๋กœ ํ๋ฃจํ”„ ํ˜•ํƒœ์˜ ์‹œ๊ฐ„-์ตœ์  ์ ˆํ™˜ ๋ฐฉ๋ฒ•์„ ์ œ์•ˆํ•œ๋‹ค. ์ œ์•ˆํ•˜๋Š” ๋ฐฉ๋ฒ•์€ ๋ฐ๋“œ๋น„ํŠธ(Dead-beat) ์ œ์–ด ๊ตฌ์กฐ๋ฅผ ์ทจํ•˜๋ฉฐ, ์ž์† ๋ฒกํ„ฐ ์˜ˆ์ธก์„ ํ†ตํ•˜์—ฌ ์ž์†์ด ์‹œ๊ฐ„-์ตœ์ ์˜ ๊ฒฝ๋กœ๋ฅผ ๋”ฐ๋ฅด๋„๋ก ์ „์•• ๋ฒกํ„ฐ๋ฅผ ์ธ๊ฐ€ํ•œ๋‹ค. ๋ณธ ๋…ผ๋ฌธ์—์„œ๋Š” ์‹œ๊ฐ„-์ตœ์  ์ ˆํ™˜ ๋ฐฉ๋ฒ•์„ ์ ์šฉํ•œ ์ „๋ฅ˜ ์ œ์–ด ๊ตฌ์กฐ๋ฅผ ์ œ์•ˆํ•œ๋‹ค. ์‹œ๊ฐ„-์ตœ์  ์ ˆํ™˜ ๋ฐฉ๋ฒ•์„ ํ•˜์œ„ ์ œ์–ด๊ธฐ๋กœ ๊ตฌ์„ฑํ•˜์—ฌ ์‹์Šค-์Šคํ… ์šด์ „์˜ ๋™ํŠน์„ฑ์„ ํ™•๋ณดํ•˜๋ฉฐ, ์ƒ์œ„ ์ „๋ฅ˜ ์ œ์–ด๊ธฐ๋ฅผ ํ†ตํ•˜์—ฌ ์ „๋ฅ˜ ์ œํ•œ์— ๋Œ€ํ•œ ๋ชจ๋‹ˆํ„ฐ๋ง ๋ฐ ํ† ํฌ ์ œ์–ด๋ฅผ ์ˆ˜ํ–‰ํ•œ๋‹ค. 30 kW ๊ธ‰ ํ•˜์ด๋ธŒ๋ฆฌ๋“œ ์ž๋™์ฐจ ๊ฒฌ์ธ์šฉ IPMSM์„ ๋Œ€์ƒ์œผ๋กœ, ์ œ์•ˆํ•˜๋Š” ๋ฐฉ๋ฒ•์˜ ์„ฑ๋Šฅ์„ ์‹œ๋ฎฌ๋ ˆ์ด์…˜ ๋ฐ ์‹คํ—˜์œผ๋กœ ๊ฒ€์ฆํ•˜์˜€๋‹ค. ์ œ์•ˆํ•˜๋Š” ๋ฐฉ๋ฒ•์„ ํ†ตํ•˜์—ฌ ์‹์Šค-์Šคํ… ์šด์ „์˜ ๋™ํŠน์„ฑ์„ ํ˜„์ €ํžˆ ๊ฐœ์„ ํ•  ์ˆ˜ ์žˆ์Œ์„ ๋ณด์˜€๋‹ค.Six-step operation of a three-phase inverter maximizes the utilization of dc-link voltage using only the six vertices of the voltage hexagon. Thus, the six-step operation can enhance the torque capability of ac motors. Furthermore, the switching loss of the inverter is conspicuously reduced compared to the PWM operation. Due to the advantages of the six-step operation, a number of studies have been conducted on the six-step operation. Since the magnitude of the output voltage is maximized under the six-step operation, the phase angle of the output voltage remains as the only degree of freedom. Focusing on the voltage angle, most research has modeled the six-step operation of a permanent-magnet synchronous motor (PMSM) as a linear system with a change in the fundamental component of the voltage angle; the controllers have been designed based on the frequency domain analysis with a linearized model. However, this model is based on small signal analysis near the equilibrium point. This means that the accuracy of the large signal is not guaranteed. In addition, the frequency domain analysis only focuses on the fundamental component of the output voltage, so it does not take into account the effect of the harmonic component on the dynamic performance. This modeling error makes it difficult to improve the dynamic performance of the six-step operation. This thesis presents a method for improving the dynamic performance of PMSMs six-step operation. In the rotor reference frame, the instantaneous voltage vector of the six-step operation has the effect of rotating in the opposite direction of the rotor. In this thesis, the analysis proceeds in the time domain to reflect the effects of the instantaneous voltage. The instantaneous trajectory of the stator flux-linkage is formulated according to the time interval of the applied voltage. A time-optimal transition method for the six-step operation of PMSM is theoretically derived from this formulation. In the rotor reference frame, the time-optimal path of the flux vector seems like a detour to the target locus. It is difficult to implement using a linear regulator designed in the rotor reference frame, and an open-loop structure is needed. In contrast, in the stationary reference frame, the time-optimal path appears as a shortcut when the output torque increases and a detour when the output torque decreases. Based on the analysis in the stationary reference frame, this thesis proposes a closed-loop time-optimal transition method. The proposed method utilizes a dead-beat control structure and applies a voltage vector so that the flux vector follows a time-optimal path through the prediction. This thesis also proposes a current control structure to be used in conjunction with the previously mentioned time-optimal transition method. By configuring the time-optimal transition method as an inner controller, the dynamic performance of the six-step operation is secured; the torque control with the current limit monitoring is performed through the outer current controller. The performance of the proposed method is verified through simulation and experiments for a 30 kW-IPMSM for HEV application. It is shown that the dynamic performance of the six-step operation can be conspicuously improved through the proposed method.์ œ 1์žฅ ์„œ๋ก  1 1.1 ์—ฐ๊ตฌ์˜ ๋ฐฐ๊ฒฝ 1 1.2 ์—ฐ๊ตฌ์˜ ๋ชฉ์  7 1.3 ๋…ผ๋ฌธ์˜ ๊ตฌ์„ฑ 9 ์ œ 2์žฅ ์‹์Šค-์Šคํ… ์šด์ „ ์ œ์–ด์— ๊ด€ํ•œ ๊ธฐ์กด ์—ฐ๊ตฌ 10 2.1 ์ง์ ‘ ํ† ํฌ ์ œ์–ด ๊ตฌ์กฐ๋ฅผ ์ด์šฉํ•œ ์‹์Šค-์Šคํ… ์šด์ „ 10 2.1.1 ์ •์ƒ์ƒํƒœ ํ† ํฌ ์‹ ๊ธฐ๋ฐ˜์˜ ๋ฐฉ๋ฒ• [20]-[27] 10 2.1.2 PMSM์˜ ๋™ํŠน์„ฑ์„ ๊ณ ๋ คํ•œ ์ „์••๊ฐ ์ œ์–ด [28], [29] 14 2.2 ์ „๋ฅ˜ ์ œ์–ด ๊ตฌ์กฐ๋ฅผ ์ด์šฉํ•œ ์‹์Šค-์Šคํ… ์šด์ „ 17 2.2.1 ์ „์•• ์ง€๋ น ์ˆ˜์ • ๋ฐฉ๋ฒ•์„ ํ†ตํ•œ ์‹์Šค-์Šคํ… ์šด์ „ [30] 17 2.2.2 ๊ฐ€๋ณ€ ์ธ๊ฐ€ ์‹œ๊ฐ„ ์ œ์–ด๋ฅผ ํ†ตํ•œ q์ถ• ์ „๋ฅ˜ ์ œ์–ด [35] 21 2.3 ๋ฐ๋“œ๋น„ํŠธ ์ž์† ์ œ์–ด ๊ตฌ์กฐ๋ฅผ ์ด์šฉํ•œ ์‹์Šค-์Šคํ… ์šด์ „ 24 ์ œ 3์žฅ ๋ชจ๋ธ ๊ธฐ๋ฐ˜์˜ ์‹œ๊ฐ„-์ตœ์  ์šด์ „์  ์ ˆํ™˜ 28 3.1 ์˜๊ตฌ์ž์„ ์ „๋™๊ธฐ์˜ ์‹์Šค-์Šคํ… ์šด์ „ ๋ชจ๋ธ๋ง 29 3.1.1 ์‹์Šค-์Šคํ… ์šด์ „์˜ ์ˆœ์‹œ ์ „์•• ๋ฒกํ„ฐ 29 3.1.2 ์˜๊ตฌ์ž์„ ์ „๋™๊ธฐ์˜ ์ž์† ๊ถค์  ๋ชจ๋ธ๋ง 31 3.1.3 ์ •์ƒ์ƒํƒœ ์ž์† ๊ถค์  33 3.1.4 ์ ˆํ™˜์— ๋”ฐ๋ฅธ ์ž์† ๊ถค์  36 3.2 ์šด์ „์  ์ ˆํ™˜ ๋ฐฉ๋ฒ•์— ๋Œ€ํ•œ ๋ถ„์„ 38 3.2.1 ํ•œ ๋‹จ๊ณ„์— ๊ฑธ์นœ ์ ˆํ™˜ 40 3.2.2 ๋‘ ๋‹จ๊ณ„์— ๊ฑธ์นœ ์ ˆํ™˜ 42 3.2.3 ์„ธ ๋‹จ๊ณ„์— ๊ฑธ์นœ ์ ˆํ™˜ 43 3.2.4 ๋„ค ๋‹จ๊ณ„์— ๊ฑธ์นœ ์ ˆํ™˜ 48 3.3 ์‹œ๋ฎฌ๋ ˆ์ด์…˜ ๋ฐ ์‹คํ—˜ ๊ฒ€์ฆ 52 3.3.1 ์ œ์•ˆํ•˜๋Š” ์ ˆํ™˜ ๋ฐฉ๋ฒ•์˜ ๊ตฌํ˜„ ๋ฐ ๊ฒ€์ฆ 52 3.3.2 ์‹œ๋ฎฌ๋ ˆ์ด์…˜ ๊ฒฐ๊ณผ 56 3.3.3 ์‹คํ—˜ ๊ฒฐ๊ณผ 60 3.4 ๋ชจ๋ธ ๊ธฐ๋ฐ˜ ๊ฐœ๋ฃจํ”„ ์ ˆํ™˜ ๋ฐฉ๋ฒ•์˜ ํ•œ๊ณ„์  65 ์ œ 4์žฅ ์ž์† ๋ฒกํ„ฐ ์˜ˆ์ธก์„ ํ†ตํ•œ ์‹œ๊ฐ„-์ตœ์  ์šด์ „์  ์ ˆํ™˜ ๋ฐฉ๋ฒ• 66 4.1 ์ •์ง€ ์ขŒํ‘œ๊ณ„ ์ƒ์—์„œ์˜ ์ž์† ๊ถค์  ๋ถ„์„ 67 4.1.1 ์ •์ƒ์ƒํƒœ ์ž์† ๊ถค์  67 4.1.2 ์šด์ „์  ์ ˆํ™˜ ์‹œ ์ž์† ๊ถค์  71 4.1.3 ๋น„์ธ์ ‘ ์ „์•• ๋ฒกํ„ฐ ๋ฐ PWM์„ ์ด์šฉํ•œ ์ ˆํ™˜ ๋ฐฉ๋ฒ• ๊ฒ€ํ†  75 4.2 ์ œ์•ˆํ•˜๋Š” ๋ฐฉ๋ฒ•์˜ ๊ตฌ์„ฑ 80 4.2.1 ์ •์ง€ ์ขŒํ‘œ๊ณ„ ์ž์† ์ถ”์ •๊ธฐ 80 4.2.2 ์ž์† ์ง€๋ น ์ƒ์„ฑ๊ธฐ 83 4.2.3 ์˜ˆ์ธก ๊ธฐ๋ฐ˜์˜ ์ž์† ์ œ์–ด๊ธฐ 85 4.2.4 ํ†ฑ๋‹ˆ ๋ฐ˜์†กํŒŒ ๊ธฐ๋ฐ˜์˜ ์ „์•• ๋ฒกํ„ฐ ์Šค์œ„์นญ 88 4.3 ์‹œ๋ฎฌ๋ ˆ์ด์…˜ ๋ฐ ์‹คํ—˜ ๊ฒฐ๊ณผ 89 4.3.1 ์‹œ๋ฎฌ๋ ˆ์ด์…˜ ๊ฒฐ๊ณผ 89 4.3.2 ์‹คํ—˜ ๊ฒฐ๊ณผ 96 4.4 ์ œ์•ˆํ•˜๋Š” ์‹œ๊ฐ„-์ตœ์  ์ ˆํ™˜ ๋ฐฉ๋ฒ•์˜ ์ „๋‹ฌ ํ•จ์ˆ˜ ๋ถ„์„ 102 ์ œ 5์žฅ ์‹œ๊ฐ„-์ตœ์  ์ ˆํ™˜ ๋ฐฉ๋ฒ•์„ ์ ์šฉํ•œ ํ† ํฌ ์ œ์–ด 105 5.1 ์ œ์–ด ๊ตฌ์กฐ์— ๋Œ€ํ•œ ๊ฒ€ํ†  105 5.1.1 ์ฐธ์กฐํ‘œ๋ฅผ ์ด์šฉํ•˜๋Š” ๊ตฌ์กฐ 105 5.1.2 ์ง์ ‘ ํ† ํฌ ์ œ์–ด ๊ตฌ์กฐ 106 5.1.3 ์ž์† ๊ธฐ์ค€ ์ œ์–ด ๊ตฌ์กฐ 108 5.2 ์ œ์•ˆํ•˜๋Š” ์‹์Šค-์Šคํ… ์šด์ „ ์ œ์–ด 111 5.2.1 SFOC q์ถ• ์ „๋ฅ˜ ์ œ์–ด ๊ตฌ์กฐ 111 5.2.2 ์ œ์–ด๊ธฐ ์„ค๊ณ„ ๊ณ ๋ ค ์‚ฌํ•ญ 112 5.2.3 ์ œ์–ด๊ธฐ ํ˜•ํƒœ์— ๋”ฐ๋ฅธ ์†Œ์‹ ํ˜ธ ์ „๋‹ฌ ํ•จ์ˆ˜ ๋ถ„์„ 115 5.2.4 ์ œ์–ด๊ธฐ ์ด๋“ ์„ค์ • 120 5.3 ์‹œ๋ฎฌ๋ ˆ์ด์…˜ ๋ฐ ์‹คํ—˜ ๊ฒฐ๊ณผ 127 5.3.1 ์‹œ๋ฎฌ๋ ˆ์ด์…˜ ๊ฒฐ๊ณผ 127 5.3.2 ์‹คํ—˜ ๊ฒฐ๊ณผ 133 ์ œ 6์žฅ ๊ธฐ์ € ์†๋„ ๋ถ€๊ทผ PWM ๋ชจ๋“œ์™€์˜ ์ ˆํ™˜ 141 6.1 ๊ณผ๋ณ€์กฐ ์˜์—ญ์—์„œ์˜ ์ „๋ฅ˜ ์ œ์–ด 143 6.1.1 ์—ญ์—ฐ์‚ฐ ์•ˆํ‹ฐ ์™€์ธ๋“œ์—…์˜ ์˜ํ–ฅ [62] 143 6.1.2 ์ „์•• ์ง€๋ น ์ˆ˜์ •์„ ํ†ตํ•œ ์ „๋ฅ˜ ๋™ํŠน์„ฑ ๊ฐœ์„  ๋ฐฉ๋ฒ• [30] 153 6.1.3 ๋Šฅ๋™ ์ €ํ•ญ์„ ์ด์šฉํ•œ ๋ณต์†Œ ๋ฒกํ„ฐ ์ „๋ฅ˜ ์ œ์–ด๊ธฐ ๋™ํŠน์„ฑ ๊ฐœ์„  156 6.2 PWM ๋ชจ๋“œ์™€ ์‹์Šค-์Šคํ… ๋ชจ๋“œ ๊ฐ„์˜ ์ ˆํ™˜ ๋ฐฉ๋ฒ• 161 6.3 ์‹œ๋ฎฌ๋ ˆ์ด์…˜ ๋ฐ ์‹คํ—˜ ๊ฒฐ๊ณผ 163 6.3.1 ์‹œ๋ฎฌ๋ ˆ์ด์…˜ ๊ฒฐ๊ณผ 163 6.3.2 ์‹คํ—˜ ๊ฒฐ๊ณผ 166 ์ œ 7์žฅ ๊ฒฐ๋ก  170 7.1 ์—ฐ๊ตฌ ๊ฒฐ๊ณผ 170 7.2 ํ–ฅํ›„ ๊ณผ์ œ ๋ฐ ํ›„์† ์—ฐ๊ตฌ 172 ๋ถ€ ๋ก 173 ์ฐธ๊ณ  ๋ฌธํ—Œ 185 Abstract 189๋ฐ•

    Design Simulation and Experiments on Electrical Machines for Integrated Starter-Generator Applications

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    This thesis presents two different non-permanent magnet machine designs for belt-driven integrated starter-generator (B-ISG) applications. The goal of this project is to improve the machine performance over a benchmark classical switched reluctance machine (SRM) in terms of efficiency, control complexity, torque ripple level and power factor. The cost penalty due to the necessity of a specially designed H-bridge machine inverter is also taken into consideration by implementation of a conventional AC inverter. The first design changes the classical SRM winding configuration to utilise both self-inductance and mutual-inductance in torque production. This allows the use of AC sinusoidal current with lower cost and comparable or even increased torque density. Torque density can be further increased by using a bipolar square current drive with optimum conduction angle. A reduction in control difficulty is also achieved by adoption of standard AC machine control theory. Despite these merits, the inherently low power factor and poor field weakening capability makes these machines unfavourable in B-ISG applications. The second design is a wound rotor synchronous machine (WRSM). From FE analysis, a six pole geometry presents a lower loss level over four pole geometry. Torque ripple and iron loss are effectively reduced by the use of an eccentric rotor pole. To determine the minimum copper loss criteria, a novel algorithm is proposed over the conventional Lagrange method, where the deviation is lowered from ยฑ 10% to ยฑ 1%, and the simulation time is reduced from hours to minutes on standard desktop PC hardware. With the proposed design and control strategies, the WRSM delivers a comparable field weakening capability and a higher efficiency compared with the benchmark SRM under the New European Driving Cycle, where a reduction in machine losses of 40% is possible. Nevertheless, the wound rotor structure brings mechanical and thermal challenges. A speed limit of 11,000 rpm is imposed by centrifugal forces. A maximum continuous motoring power of 3.8 kW is imposed by rotor coil temperature performance, which is extended to 5 kW by a proposed temperature balancing method. A prototype machine is then constructed, where the minimum copper loss criteria is experimentally validated. A discrepancy of no more than 10% is shown in back-EMF, phase voltage, average torque and loss from FE simulation

    Torque Control

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    This book is the result of inspirations and contributions from many researchers, a collection of 9 works, which are, in majority, focalised around the Direct Torque Control and may be comprised of three sections: different techniques for the control of asynchronous motors and double feed or double star induction machines, oriented approach of recent developments relating to the control of the Permanent Magnet Synchronous Motors, and special controller design and torque control of switched reluctance machine
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