In this report we consider the radar cross section (RCS) of a single rectangular patch antenna in a recessed cavity. Using a previously developed finite element-boundary integral method code, a study is performed on the patch's RCS as a function of frequency. To reduce the RCS of the patch at the resonant frequency, lumped (resistive) loads are placed at the edges of the patch. The effects of the lumped loads on the patch's RCS and gain are examined and it is observed that the RCS and gain are reduced as the as the load value decreases, whereas the antenna's bandwidth is increased. At resonance, the usual relations between the RCS and gain is observed, but it is shown that this relation no longer holds at frequencies away from resonance

Alexanian, Angelos

Volakis, John L.

English

NASA Technical Reports Server

N92-22 148
_J
RCS Reduction of a Microstrip Patch
Using Lumped Loads
//
John L. Volalds and Angelos Alexanian
Abstract
In this report we consider the RCS of a single rectangular patch an-
tenna in a recessed cavity. Using a previously developed finite element-
boundary integral code, a study is performed on the patch's RCS as
a function of frequency. To reduce the RCS of the patch at the reso-
nant frequency, lumped (resistive) loads are placed at the edges of the
patch. The effect of the lumped loads on the patch's RCS and gain axe
examined and it is observed that the RCS and gain axe reduced as the
load value decreases, whereas the antenna's bandwidth is increased.
At resonance, the usual relation between RCS and gain is observed,
but itisshown that this relationno longer holds at frequenciesaway
from resonance.
https://ntrs.nasa.gov/search.jsp?R=19920012905 2020-03-17T11:57:18+00:00Z
Investigation's Scope
The purpose of this study is to (see figure I):
• Study the RCS vs. Gain of the microstrip antenna by placing lumped
resistive loads at the side aperture of the patch
• Determine the resonant frequency shiK due to loading
• Assess bandwidth enhancement due to loading
This study was performed by using the University of Michigan program CAV-
ITY3D (see Appendices). Other schemes for reducing the RCS of the patch
and cavity edges using R-cards and dielectric coating are illustrated in figures
1 and 2, but these have not yet been considered.
Description of Investigation
To assess the effect of lumped loads on the RCS and Gain of the microstrip
patch we considered a 5cm x 3.4cm rectangular patch whose discretized form
is shown in figure 3. This patch is loaded with four resistors placed roughly
at the midpoint of each side as shown in figures 2 and 3. The thickness of
the substrate/cavity was 0.17558cm and the relative dielectric constant was
chosen to be _. = 2.17. Also, for input impedance and gain computations
the probe feed was placed at the bottom left corner of the patch as shown in
figure 3.
For the above patch, the resonant frequency was found to be f0 =
1.94675GHz with the resistance of each load set at 1500ft (essentially un-
loaded). At this frequency we proceeded to evaluate the Gain and RCS of
the patch as the resistance was changed from 15000 down to zero Ohms
(shorted). The normalized values of these quantities as a function of load
resistance are plotted in figure 4 and it is clear from this data that the RCS
reduction is twice (in dB) that of the Gain (the RCS in figure 4 was computed
with no load at the feed). This is to be expected since the RCS at resonance
is given by [1]
a(0,¢) = -7- {G'(O,¢)} _
or
101oga(8,¢) = 2 {101og[G'(0, ¢)] + 101og[A/vffl}
2
where 10log (7' is the Gain in dB and includes any losses due to lumped or
distributed loads. Let us assume that for a given load #1, the Gain is G_
and for another load #2, the Gain is G_. The corresponding cross sections
evaluated at the same frequency are then given by
A
10 log a, = 20 log G', + 10 log _rr
10 log o'2 = 20 log G_ + 10 log
Va-
Subtracting these equations we obtain
AadB = 10(log al -- log o.2) = 2110 log G1 - 10 log G2]
or
Aaas = 2[Ga_ - G2aB] = 2AGds
which clearly shows that the dB RCS reduction is twice the dB gain reduc-
tion.
As expected, the input impedance becomes reactive with the addition
of lumped loads and furthermore its real part is reduced in parallel with
the lumped loads. Thus the patch's resonant frequency changes with the
value of the applied load. The specific values are illustrated in figure 5
and the reason for the input resistance's reduction is that the lumped loads
placed between the patch edges and the ground are in a parallel arrangement
with the impedance originally observed at the feed. However, we note that
the radiation patterns are essentially unaffected by the placement of the
loads (see figures 6(a) and 6(b)). More specifically, the radiation pattern
corresponding to the 30012 loads is completely identical to that associated
with the unloaded patch. We will thus choose to retune the patch with this
load placed at its four side apertures (in actuality only the loads at two of
the apertures are of significance since the field at the midpoint of the other
two vanishes when the patch is at resonance).
The resonant frequency (the frequency at which the input impedance is
real) with the feed at the lower left corner (x = 1.25, y = 0.85 position)
of the patch and with the 30012 loads at the patch edges was found to be
f0 = 1.97GHz. As given in figure 7 the input resistance at this frequency
is approximately 103.512, and as shown in this figure, the input impedance
3
changesrathersubstantiallyasthe feed position changes. Interestingly, when
the feed is at (z = 2.5cm, y = 1.7cm), the input impedance is again real
and equal to approximately 49f/, a value which matches the characteristic
impedance of common coaxial cables. From fig. 7, it is also observed that
the gain is essentially unaffected by the feed's position implying that the
radiation pattern is also unaffected.
With the feed at (z = 2.5cm, y = 1.7cm) and the 300fl loads at the patch
edges, we next examined the patch VSWR and bandwidth. The results are
given in figures 8 and 9, and the assumed source/line impedance was that
at fo = 1.97GHz (i.e., Zo = 49f_). It is seen that the patch bandwidth is
increased substantially from fig. 8. Specifically, the bandwidth of the 300n
loaded patch is approximately 0.13 (normalized frequency range within which
VSWR< 3) whereas that of the unloaded patch is only 0.02 (more than six
times smaller). The RCS of the 300f_ loaded patch in the vicinity of the
resonant frequency is shown in figure 10 with or without a load of 49f_ across
the patch at the feed point. As expected, the RCS is maximum at the
resonant frequency and then drops rather rapidly away from this frequency.
When the 49f_ load is placed at the feed to simulate the presence of the
coax line, a 7dB reduction is observed at the resonant frequency. A more
extensive frequency sweep of RCS for different loading configurations can be
seen in figure 11. Here we are comparing an unloaded patch to one loaded
with four 300ft resistors and to another loaded with four 300_2 along with
the 49f_ at the feed (coax line simulation). Again we observe the expected
RCS reduction at the points of resonance.
Conclusions
One can readily conclude from the above study that the RCS of a patch
at resonance can be substantially reduced by placing lumped loads at its
side edges. The reduction in RCS achieved in this manner is about twice
(in dB) the corresponding reduction in gain. It was also noted that the
resonant frequency is a function of the load's value and thus the patch must
be retuned for each load. Alternatively, it was shown that the feed location
can be moved to again achieve resonance or simply to find an input resistance
that matches that of the feeding fine.
4
Future Study
During the next month we shall investigate the RCS and gain of the patch
when a dielectric coating is placed on its upper surface. Also the effect of
a uniform R-card across the aperture will be studied. For the first case, a
modification of the program is required.
References
[1] David R. Jackson, "The RCS of a Rectangular Microstrip Patch in a
Substrate-Superstrate Geometry," IEEE Trans. Antennas and Propa-
gat., AP-38, pp. 2-8, Jan. 1990.
.5
Appendices
Gain Calculations from Program Output Parameters
By definition,
Gain=G'(O,¢)= lim 4rr2"'_g'E"O'-"2---L_l( d)[
f -'*OO p_
where E _ is the radiated field as a function of the spherical angles 0 and _b,
Zo is the free space intrinsic impedance, r is the distance to the observation
point and P'm denotes the input power. For a probe feed, we have that
P.,,,-- _Vl'- ½Rml/12-- _R,.,
since I = 1Amp., in which Rt,, = Re {Zi,} is the antenna input resistance.
It then follows that
4_r (_-_'_) 2 IE'(0, *)12 ,
c'(0, ¢) = ZoP_ _
in which A_ denotes the wavelength in centimeters. The dB value of this
expression is computed as
G_B(0,¢ ) - 10log m 4r IE'(0,¢)I _ + 101og,okZoRa=j
The first term in this expression is that computed by the program CAV-
ITY3D and is referred to in that program as the radiated power. The second
term must therefore be added externally from the computed value of Ri. also
given by the program.
RCS Calculation from Program Output Parameters
The RCS computed by the program CAVITY3D isgivenin dB above a square
wavelength. To obtain the RCS insquare meters the followingformula must
be applied externally:
O'dBSM -" adBSW @ 20 loglo(Am )
where Am is the wavelength in meters.
-6
RCS Reduction Studies
• Resistive cards
• Lumped loads
• Shape
• Feed mechanism
Uniform Dielectric
Substrate Dielectric
. .Coating on
tapered _ JPatch Tapered
C
Lumped Tapered
Loads R Card
Study RCS vs gain characteristics for various
load treatments
Study resonant frequency shift due to loading
Study bandwidth enhancement as a function
of loading
Figure I
Other RCS reduction approaches
for simple elements
radiating
slot
tapered R
tuning ,
wires
4
R card strips
Tapered R Card reduces RCS of terminations without
effecting antenna parameters.
R Card strips act as lumped loads in reducing the RCS.
They reduce RCS and Gain, but RCS is usually reduced
much more.
• Patch must be retuned after loading.
• Radiation pattern is generally uneffected.
• Surface wave effects are suppressed because of cavity
enclosure.
Goal: Given certain criteria with respect to Gain, bandwidth,
and RCS at the design-frequency, what should be the
loading, feed mechanism and structural characteristics
of the patch antenna?
Figure 2
z Actual element dimensions for the following patch and cavity
configurations.
.17558cm
Top View
.17cm -"_ 7.5 cm
.25cm
0 g I0
•,- Patch
v
i j
i I
I
I
I
i
I
i
i
I
I
I
I
I
I
I
26 27 20 2g 30 31
5.1 cm
• Feed
• Load
Cavity
Side View
2
I 2 3 4 _ 6 7 6 9 I0 I1 12 13 14 15 16 17 I0 Ig 20 21 22 23 24 25 26 27 28 2g 30 31
I7S.58cm
T
Patch dimensions : x-5.0cm, y=3.4cm
Figure 3
0.000
-3.OO
-6.OO
-9.00
-12.0
-15.0
-18.0
-21.0
-24.0
-27.0
-30.0
°°
o•"
NormalizedGainindB
Normalized RCS in dB
0 300 600 900 1200 1500
Load Resistance in Ohms
Figure 4
350.
300.
250.
200,
150.
100.
50.0
0.000
-50.0
#s
s*
s •
_ S
•o
_ I
p•,
BB _
t
S o
I I
a _
Radiation Intensity = 4_ IEscat.12
Input Resistance in Ohms
Input Reactance
Gain in dB
RCS in dBsm
rib .LI .l_
..o...°1°. ................ . ............ . .... _--m _1
• , I , . . I , . . I I
0 300 600 900 1200 1500
Load Resistance in Ohms
Figure 5
0.000
-5.00
-10.0
-15.0
-20.0
Power Patterns (_0 °)
\ . .
\ , .
\
\
\
\
Load Resistance = 1500 Ohms
......... Load Resistance = 300 Ohms
...... Load Resistance = 75 Ohms
...... Load Resistance = 20 Ohms
.... Load Resistance = 10 Ohms
\
1
4
l.,].,,[,,,I.,,I,,,l,.ll,, ,I,., I
10.00 20.00 30.00 40.00 50.00 60.00 "rO.O(I '_f_O(I 90(_0
Angle 0 in degrees
Figure 6(8)
0.000
Power Patterns (0_=90 °)
-5.00
-10.0
-15.0
-20.0
-25.0
-30.0
-35.0
Load Resistance = 1500 Ohms
......... Load Resistance = 300 Ohms
Load Resistance = 75 Ohms
...... Load Resistance = 20 Ohms
..... Load Resistance = I0 Ohms
0.00 10.00 20.00 30.00 40.00 50.00 60.00 70.00 80.00 90.00
Angle O in degrees
Figure 6(b)
120.
100.
80.0
60.0
40.0
20.0
0.000
-20.0
Radiation Properties of Patch as Feed is Moved
r - - , I . , , I . . • I • • • I " " "1 " " " I " " " I " " " I " " "
Radiation Intensity = 4n IEscat.I 2
Input Resistance in Ohms
Input Reactance
Gain in dB
"4
........................ .. - ...._."-" ...................
i I | I | ii 1' I ! II II el iii II l| II n? II It _lo 2l 11 3) 14 1, 211 17 le FI )o _q
_- • Feed
• • koaa
Figure 7. The arrow on the patch above indicates the motion of the feed with
initial and final positions at nodes (6,6)-and (15,15) respectively. The frequency is
1.97GHz which happens to be the resonant frequency for four 300f2 loads and the
feed at node (6,6). With the feed at node (11,11) it is interesting to note that the
input impedance becomes approximately 50f2 (ie. 48.92-j1.13 fl).
>6.00
5.50
5.00
4.50
4.00
3.50
3.00
2.50
2.00
1.50
1.00
1.80
I
I
I
I
I
I
I
300_
loads
at edges
1.85 1.90 1.95 2.00 2.05 2.10 2.15 2.20
Frequency in GHz
Figure 8. VSWR of loaded and unloaded patch vs frequency
Computation of VSWR :
VSWR = (1+11"1)/(1-11"1) where F = (Zin-Zinr)/(Zin+Zinr)
Zinr= 48.92-j 1.13 fl is the input impedance at the resonant frequency (1.97GHz)
for four 300f2 loads and feed at node position (11,11). Note that at this frequency
VSWR=I.
Zin = input impedance for the same configuration as above, with the exception that
the frequency varies.
/Iro Ero
Figure 9. F (as defined in figure 8) vs frequency on a smith chart. Note that the
endpoints of this graph correspond to VSWR=3.
-20.0
-25.0
-30.0
-35.0
-40.0
1.80
.... I .... I .... I .... 1 .... I .... I .... I ....
......... 48.92+j1.13 Ohms at feed
.... I .... I .... I ..... 1 .... I .... I .... I ....
1.85 1.90 1.95 2.00 2.05 2.10 2.15 2.20
Frequency in GHz
Figure 10. RCS as a function of frequency
-10.0
-20.0
-30.0
._ -40.0
ue3
-50.0
-60.0
-70.0
1.00 2.00 3.00 4.00 5.00 6.00 7.00 8.00 9.00 10.00
Frequency in GHz
Figure 11. RCS as a function of frequency
7.5 5.1 .17558
31 31 2
1
(2.17,0) (1.,0.)
1.97 1.97 1
2
001
001
.01 800
2
1
66
20 20
1
2
0
1
11 11
10
1
4
15 6
(300.0.)
1
25 15
(300.0.)
1
15 25
(300.,0.)
1
6 15
(300.,0.)
1
2
cavitysizeincm (x,y,z)
number of nodes (x,y,z)
-uniformdielectric
substrate dielectric - er
frequency rain, max, increment
- radiated intensitycalculation
them rnin, max, increment
phi rain, max, increment
tolerance, number of iterations
- monitor cnvergence l=yes 2=no
number of patch
lower left comer of patch node(x,y)
number of elements on patch (x,y)
layer in which patch resides
- patch display l=yes 2=no
number of short circuit pins
number of feeds
feed position node(x,y)
amplitude and phase of current source
layer in which feed is embedded
number of loads
node(x,y) load 1 position
value of load 1 (complex) in
layer in which load 1 is embedded
node(x,y) load 2 position
value of load 2 (complex) in £'/
layer in which load 2 is embedded
node(x,y) load 3 position
value of load 3 (complex) in t2
layer in which load 3 is embedded
node(x,y) load 4 position
value of load 4 (complex) in t2
layer in which load 4 is embedded
- resistive card l=yes 2=no
Figure 12
Side View
5.] cm
¼
'll Ii I i"i"if'f'l'TiiiiY'_"T'i"T'i"iiYi _ ] __ J.,_,______
1 I 2 3 4 5 6 7 8 9 I0 I1 12 13 14 15 i6 17 I0 t9 24 21 22 23 24 2S 26 27 211 29 $0 31 --_
Patch dimensions : z-5.0cm, y-3.4cm
Figure 13. This is the exact patch-cavity configuration resulting from the input
file given in figure 12.
31
3O
29
2O
27
26
2S
24
23
22
21
_0
19
I0
17
16
iS
14
13
t2 i
II
I0
! 2 3
v
X
4 S 6 7 8 9 I0 II f2 13 14 IS 16 17 tO 19 20 21 22 23 24 25 26 27 20 29 30 3t
FiL,ure 14. Exn-a grid for future designs.


RCS reduction of a microstrip patch using lumped loads

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