1,509 research outputs found

    Voltage noise analysis with ring oscillator clocks

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    Voltage noise is the main source of dynamic variability in integrated circuits and a major concern for the design of Power Delivery Networks (PDNs). Ring Oscillators Clocks (ROCs) have been proposed as an alternative to mitigate the negative effects of voltage noise as technology scales down and power density increases. However, their effectiveness highly depends on the design parameters of the PDN, power consumption patterns of the system and spatial locality of the ROCs within the clock domains. This paper analyzes the impact of the PDN parameters and ROC location on the robustness to voltage noise. The capability of reacting instantaneously to unpredictable voltage droops makes ROCs an attractive solution, which allows to reduce the amount of decoupling capacitance without downgrading performance. Tolerance to voltage noise and related benefits can be increased by using multiple ROCs and reducing the size of the clock domains. The analysis shows that up to 83% of the margins for voltage noise and up to 27% of the leakage power can be reduced by using local ROCs.Peer ReviewedPostprint (author's final draft

    Adaptive clock with useful jitter

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    Report - Departament Ciรจncies de la ComputaciรณThe growing variability in nanoelectronic devices due to uncertainties from the manufacturing process and environmental conditions (power supply, temperature, aging) requires increasing design guardbands, forcing circuits to work with conservative clock frequencies. Various schemes for clock generation based on ring oscillators have been proposed with the goal to mitigate the power and performance losses attributable to variability. However, there has been no systematic analysis to quantify the benefits of such schemes.This paper presents and analyzes an Adaptive Clocking scheme with Useful Jitter (ACUJ) that uses variability as an opportunity to reduce power by adapting the clock frequency to the varying environmental conditions and, thus, reducing guardband margins significantly. Power can be reduced between 20% and 40% at iso-performance and performance can be boosted by similar amounts at iso-power. Additionally, energy savings can be translated to substantial advantages in terms of reliability and thermal management. More importantly, the technology can be adopted with minimal modifications to conventional EDA flows.Postprint (published version

    A 10-Gb/s two-dimensional eye-opening monitor in 0.13-ฮผm standard CMOS

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    An eye-opening monitor (EOM) architecture that can capture a two-dimensional (2-D) map of the eye diagram of a high-speed data signal has been developed. Two single-quadrant phase rotators and one digital-to-analog converter (DAC) are used to generate rectangular masks with variable sizes and aspect ratios. Each mask is overlapped with the received eye diagram and the number of signal transitions inside the mask is recorded as error. The combination of rectangular masks with the same error creates error contours that overall provide a 2-D map of the eye. The authors have implemented a prototype circuit in 0.13-ฮผm standard CMOS technology that operates up to 12.5 Gb/s at 1.2-V supply. The EOM maps the input eye to a 2-D error diagram with up to 68-dB mask error dynamic range. The left and right halves of the eyes are monitored separately to capture horizontally asymmetric eyes. The chip consumes 330 mW and operates reliably with supply voltages as low as 1 V at 10 Gb/s. The authors also present a detailed analysis that verifies if the measurements are in good agreement with the expected results

    Quantum Communication Uplink to a 3U CubeSat: Feasibility & Design

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    Satellites are the efficient way to achieve global scale quantum communication (Q.Com) because unavoidable losses restrict fiber based Q.Com to a few hundred kilometers. We demonstrate the feasibility of establishing a Q.Com uplink with a tiny 3U CubeSat (measuring just 10X10X32 cm^3 ) using commercial off-the-shelf components, the majority of which have space heritage. We demonstrate how to leverage the latest advancements in nano-satellite body-pointing to show that our 4kg CubeSat can provide performance comparable to much larger 600kg satellite missions. A comprehensive link budget and simulation was performed to calculate the secure key rates. We discuss design choices and trade-offs to maximize the key rate while minimizing the cost and development needed. Our detailed design and feasibility study can be readily used as a template for global scale Q.Com.Comment: 24 pages, 9 figures, 2 tables. Fixed tables and figure

    A study of phase noise and jitter in submicron CMOS phase-locked loop circuits

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    Phase-locked loops (PLLs) are widely used in communication systems. With the continuously expanding of market for high speed, portable communication devices, low noise CMOS submicron integrated circuit designs of PLL for different applications are in large demand. In this dissertation, phase noise and jitter properties of PLL and its building blocks are investigated both at the physical and system levels. At the physical level, hot carrier effect in submicron MOSFETs has been considered. As one of the most dominant noise sources of PLL, the voltage-controlled oscillator (VCO) is considered when investigating the noise degradation induced by the hot carrier effect. Experimental results of jitter degradation due to hot carrier effects are presented for different ring oscillator types VCOs designed in 0.5 micron n-well CMOS technology. An increase in RMS jitter by 25% and 10% decrease in oscillation frequency of VCO can be observed after 4 hours hot carrier stress. The hot carrier induced noise degradation on PLL is also presented based on the performance degradation in VCO. Simulation results show 40% decrease in VCO gain after 4 hours stress and a 23% decrease in damping factor and loop bandwidth. Moreover, degradation on PLL noise performance includes a left shift peak in phase noise and a 17% increase in RMS jitter. At the system level, noise sources in a PLL system are investigated including the input reference noise, VCO noise and the frequency divider noise. Phase noise prediction method for PLL is developed. Experimental phase noise measurement results on 0.5 micron CMOS PLL systems based on different types of VCOs are in close agreement with the predicted phase noise. Therefore, the phase noise prediction method is verified. On the other hand, a 3 GHz adaptive bandwidth PLL based on LC-VCO is designed in 0.25 micron n-well CMOS technology to investigate the phase noise and jitter performance by varying the loop parameters. By considering the noise simulation results based on the adaptive bandwidth feature and the quality factor of the on-chip inductor, PLL loop parameters can be carefully chosen at the design phase to achieve an optimal noise performance

    ํ†ต๊ณ„์  ์ฃผํŒŒ์ˆ˜ ๊ฒ€์ถœ๊ธฐ ๊ธฐ๋ฐ˜ ๊ธฐ์ค€ ์ฃผํŒŒ์ˆ˜๋ฅผ ์‚ฌ์šฉํ•˜์ง€ ์•Š๋Š” ํด๋ก ๋ฐ ๋ฐ์ดํ„ฐ ๋ณต์› ํšŒ๋กœ์˜ ์„ค๊ณ„ ๋ฐฉ๋ฒ•๋ก 

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    ํ•™์œ„๋…ผ๋ฌธ(๋ฐ•์‚ฌ) -- ์„œ์šธ๋Œ€ํ•™๊ต๋Œ€ํ•™์› : ๊ณต๊ณผ๋Œ€ํ•™ ์ „๊ธฐยท์ •๋ณด๊ณตํ•™๋ถ€, 2022. 8. ์ •๋•๊ท .In this thesis, a design of a high-speed, power-efficient, wide-range clock and data recovery (CDR) without a reference clock is proposed. A frequency acquisition scheme using a stochastic frequency detector (SFD) based on the Alexander phase detector (PD) is utilized for the referenceless operation. Pat-tern histogram analysis is presented to analyze the frequency acquisition behavior of the SFD and verified by simulation. Based on the information obtained by pattern histogram analysis, SFD using autocovariance is proposed. With a direct-proportional path and a digital integral path, the proposed referenceless CDR achieves frequency lock at all measurable conditions, and the measured frequency acquisition time is within 7ฮผs. The prototype chip has been fabricated in a 40-nm CMOS process and occupies an active area of 0.032 mm2. The proposed referenceless CDR achieves the BER of less than 10-12 at 32 Gb/s and exhibits an energy efficiency of 1.15 pJ/b at 32 Gb/s with a 1.0 V supply.๋ณธ ๋…ผ๋ฌธ์€ ๊ธฐ์ค€ ํด๋Ÿญ์ด ์—†๋Š” ๊ณ ์†, ์ €์ „๋ ฅ, ๊ด‘๋Œ€์—ญ์œผ๋กœ ๋™์ž‘ํ•˜๋Š” ํด๋Ÿญ ๋ฐ ๋ฐ์ดํ„ฐ ๋ณต์›ํšŒ๋กœ์˜ ์„ค๊ณ„๋ฅผ ์ œ์•ˆํ•œ๋‹ค. ๊ธฐ์ค€ ํด๋Ÿญ์ด ์—†๋Š” ๋™์ž‘์„ ์œ„ํ•ด์„œ ์•Œ๋ ‰์‚ฐ๋” ์œ„์ƒ ๊ฒ€์ถœ๊ธฐ์— ๊ธฐ๋ฐ˜ํ•œ ํ†ต๊ณ„์  ์ฃผํŒŒ์ˆ˜ ๊ฒ€์ถœ๊ธฐ๋ฅผ ์‚ฌ์šฉํ•˜๋Š” ์ฃผํŒŒ์ˆ˜ ํš๋“ ๋ฐฉ์‹์ด ์‚ฌ์šฉ๋œ๋‹ค. ํ†ต๊ณ„์  ์ฃผํŒŒ์ˆ˜ ๊ฒ€์ถœ๊ธฐ์˜ ์ฃผํŒŒ์ˆ˜ ์ถ”์  ์–‘์ƒ์„ ๋ถ„์„ํ•˜๊ธฐ ์œ„ํ•ด ํŒจํ„ด ํžˆ์Šคํ† ๊ทธ๋žจ ๋ถ„์„ ๋ฐฉ๋ฒ•๋ก ์„ ์ œ์‹œํ•˜์˜€๊ณ  ์‹œ๋ฎฌ๋ ˆ์ด์…˜์„ ํ†ตํ•ด ๊ฒ€์ฆํ•˜์˜€๋‹ค. ํŒจํ„ด ํžˆ์Šคํ† ๊ทธ๋žจ ๋ถ„์„์„ ํ†ตํ•ด ์–ป์€ ์ •๋ณด๋ฅผ ๋ฐ”ํƒ•์œผ๋กœ ์ž๊ธฐ๊ณต๋ถ„์‚ฐ์„ ์ด์šฉํ•œ ํ†ต๊ณ„์  ์ฃผํŒŒ์ˆ˜ ๊ฒ€์ถœ๊ธฐ๋ฅผ ์ œ์•ˆํ•œ๋‹ค. ์ง์ ‘ ๋น„๋ก€ ๊ฒฝ๋กœ์™€ ๋””์ง€ํ„ธ ์ ๋ถ„ ๊ฒฝ๋กœ๋ฅผ ํ†ตํ•ด ์ œ์•ˆ๋œ ๊ธฐ์ค€ ํด๋Ÿญ์ด ์—†๋Š” ํด๋Ÿญ ๋ฐ ๋ฐ์ดํ„ฐ ๋ณต์›ํšŒ๋กœ๋Š” ๋ชจ๋“  ์ธก์ • ๊ฐ€๋Šฅํ•œ ์กฐ๊ฑด์—์„œ ์ฃผํŒŒ์ˆ˜ ์ž ๊ธˆ์„ ๋‹ฌ์„ฑํ•˜๋Š” ๋ฐ ์„ฑ๊ณตํ•˜์˜€๊ณ , ๋ชจ๋“  ๊ฒฝ์šฐ์—์„œ ์ธก์ •๋œ ์ฃผํŒŒ์ˆ˜ ์ถ”์  ์‹œ๊ฐ„์€ 7ฮผs ์ด๋‚ด์ด๋‹ค. 40-nm CMOS ๊ณต์ •์„ ์ด์šฉํ•˜์—ฌ ๋งŒ๋“ค์–ด์ง„ ์นฉ์€ 0.032 mm2์˜ ๋ฉด์ ์„ ์ฐจ์ง€ํ•œ๋‹ค. ์ œ์•ˆํ•˜๋Š” ํด๋Ÿญ ๋ฐ ๋ฐ์ดํ„ฐ ๋ณต์›ํšŒ๋กœ๋Š” 32 Gb/s์˜ ์†๋„์—์„œ ๋น„ํŠธ์—๋Ÿฌ์œจ 10-12 ์ดํ•˜๋กœ ๋™์ž‘ํ•˜์˜€๊ณ , ์—๋„ˆ์ง€ ํšจ์œจ์€ 32Gb/s์˜ ์†๋„์—์„œ 1.0V ๊ณต๊ธ‰์ „์••์„ ์‚ฌ์šฉํ•˜์—ฌ 1.15 pJ/b์„ ๋‹ฌ์„ฑํ•˜์˜€๋‹ค.CHAPTER 1 INTRODUCTION 1 1.1 MOTIVATION 1 1.2 THESIS ORGANIZATION 13 CHAPTER 2 BACKGROUNDS 14 2.1 CLOCKING ARCHITECTURES IN SERIAL LINK INTERFACE 14 2.2 GENERAL CONSIDERATIONS FOR CLOCK AND DATA RECOVERY 24 2.2.1 OVERVIEW 24 2.2.2 JITTER 26 2.2.3 CDR JITTER CHARACTERISTICS 33 2.3 CDR ARCHITECTURES 39 2.3.1 PLL-BASED CDR โ€“ WITH EXTERNAL REFERENCE CLOCK 39 2.3.2 DLL/PI-BASED CDR 44 2.3.3 PLL-BASED CDR โ€“ WITHOUT EXTERNAL REFERENCE CLOCK 47 2.4 FREQUENCY ACQUISITION SCHEME 50 2.4.1 TYPICAL FREQUENCY DETECTORS 50 2.4.1.1 DIGITAL QUADRICORRELATOR FREQUENCY DETECTOR 50 2.4.1.2 ROTATIONAL FREQUENCY DETECTOR 54 2.4.2 PRIOR WORKS 56 CHAPTER 3 DESIGN OF THE REFERENCELESS CDR USING SFD 58 3.1 OVERVIEW 58 3.2 PROPOSED FREQUENCY DETECTOR 62 3.2.1 MOTIVATION 62 3.2.2 PATTERN HISTOGRAM ANALYSIS 68 3.2.3 INTRODUCTION OF AUTOCOVARIANCE TO STOCHASTIC FREQUENCY DETECTOR 75 3.3 CIRCUIT IMPLEMENTATION 83 3.3.1 IMPLEMENTATION OF THE PROPOSED REFERENCELESS CDR 83 3.3.2 CONTINUOUS-TIME LINEAR EQUALIZER (CTLE) 85 3.3.3 DIGITALLY-CONTROLLED OSCILLATOR (DCO) 87 3.4 MEASUREMENT RESULTS 89 CHAPTER 4 CONCLUSION 99 APPENDIX A DETAILED FREQUENCY ACQUISITION WAVEFORMS OF THE PROPOSED SFD 100 BIBLIOGRAPHY 108 ์ดˆ ๋ก 122๋ฐ•

    Fast synchronization 3R burst-mode receivers for passive optical networks

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    This paper gives a tutorial overview on high speed burst-mode receiver (BM-RX) requirements, specific for time division multiplexing passive optical networks, and design issues of such BM-RXs as well as their advanced design techniques. It focuses on how to design BM-RXs with short burst overhead for fast synchronization. We present design principles and circuit architectures of various types of burst-mode transimpedance amplifiers, burst-mode limiting amplifiers and burst-mode clock and data recovery circuits. The recent development of 10 Gb/s BM-RXs is highlighted also including dual-rate operation for coexistence with deployed PONs and on-chip auto reset generation to eliminate external timing-critical control signals provided by a PON medium access control. Finally sub-system integration and state-of-the-art system performance for 10 Gb/s PONs are reviewed

    ๊ณ ์† ์‹œ๋ฆฌ์–ผ ๋งํฌ๋ฅผ ์œ„ํ•œ ๊ณ ๋ฆฌ ๋ฐœ์ง„๊ธฐ๋ฅผ ๊ธฐ๋ฐ˜์œผ๋กœ ํ•˜๋Š” ์ฃผํŒŒ์ˆ˜ ํ•ฉ์„ฑ๊ธฐ

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    ํ•™์œ„๋…ผ๋ฌธ(๋ฐ•์‚ฌ) -- ์„œ์šธ๋Œ€ํ•™๊ต๋Œ€ํ•™์› : ๊ณต๊ณผ๋Œ€ํ•™ ์ „๊ธฐยท์ •๋ณด๊ณตํ•™๋ถ€, 2022. 8. ์ •๋•๊ท .In this dissertation, major concerns in the clocking of modern serial links are discussed. As sub-rate, multi-standard architectures are becoming predominant, the conventional clocking methodology seems to necessitate innovation in terms of low-cost implementation. Frequency synthesis with active, inductor-less oscillators replacing LC counterparts are reviewed, and solutions for two major drawbacks are proposed. Each solution is verified by prototype chip design, giving a possibility that the inductor-less oscillator may become a proper candidate for future high-speed serial links. To mitigate the high flicker noise of a high-frequency ring oscillator (RO), a reference multiplication technique that effectively extends the bandwidth of the following all-digital phase-locked loop (ADPLL) is proposed. The technique avoids any jitter accumulation, generating a clean mid-frequency clock, overall achieving high jitter performance in conjunction with the ADPLL. Timing constraint for the proper reference multiplication is first analyzed to determine the calibration points that may correct the existent phase errors. The weight for each calibration point is updated by the proposed a priori probability-based least-mean-square (LMS) algorithm. To minimize the time required for the calibration, each gain for the weight update is adaptively varied by deducing a posteriori which error source dominates the others. The prototype chip is fabricated in a 40-nm CMOS technology, and its measurement results verify the low-jitter, high-frequency clock generation with fast calibration settling. The presented work achieves an rms jitter of 177/223 fs at 8/16-GHz output, consuming 12.1/17-mW power. As the second embodiment, an RO-based ADPLL with an analog technique that addresses the high supply sensitivity of the RO is presented. Unlike prior arts, the circuit for the proposed technique does not extort the RO voltage headroom, allowing high-frequency oscillation. Further, the performance given from the technique is robust over process, voltage, and temperature (PVT) variations, avoiding the use of additional calibration hardware. Lastly, a comprehensive analysis of phase noise contribution is conducted for the overall ADPLL, followed by circuit optimizations, to retain the low-jitter output. Implemented in a 40-nm CMOS technology, the frequency synthesizer achieves an rms jitter of 289 fs at 8 GHz output without any injected supply noise. Under a 20-mVrms white supply noise, the ADPLL suppresses supply-noise-induced jitter by -23.8 dB.๋ณธ ๋…ผ๋ฌธ์€ ํ˜„๋Œ€ ์‹œ๋ฆฌ์–ผ ๋งํฌ์˜ ํด๋ฝํ‚น์— ๊ด€์—ฌ๋˜๋Š” ์ฃผ์š”ํ•œ ๋ฌธ์ œ๋“ค์— ๋Œ€ํ•˜์—ฌ ๊ธฐ์ˆ ํ•œ๋‹ค. ์ค€์†๋„, ๋‹ค์ค‘ ํ‘œ์ค€ ๊ตฌ์กฐ๋“ค์ด ์ฑ„ํƒ๋˜๊ณ  ์žˆ๋Š” ์ถ”์„ธ์— ๋”ฐ๋ผ, ๊ธฐ์กด์˜ ํด๋ผํ‚น ๋ฐฉ๋ฒ•์€ ๋‚ฎ์€ ๋น„์šฉ์˜ ๊ตฌํ˜„์˜ ๊ด€์ ์—์„œ ์ƒˆ๋กœ์šด ํ˜์‹ ์„ ํ•„์š”๋กœ ํ•œ๋‹ค. LC ๊ณต์ง„๊ธฐ๋ฅผ ๋Œ€์‹ ํ•˜์—ฌ ๋Šฅ๋™ ์†Œ์ž ๋ฐœ์ง„๊ธฐ๋ฅผ ์‚ฌ์šฉํ•œ ์ฃผํŒŒ์ˆ˜ ํ•ฉ์„ฑ์— ๋Œ€ํ•˜์—ฌ ์•Œ์•„๋ณด๊ณ , ์ด์— ๋ฐœ์ƒํ•˜๋Š” ๋‘๊ฐ€์ง€ ์ฃผ์š” ๋ฌธ์ œ์ ๊ณผ ๊ฐ๊ฐ์— ๋Œ€ํ•œ ํ•ด๊ฒฐ ๋ฐฉ์•ˆ์„ ํƒ์ƒ‰ํ•œ๋‹ค. ๊ฐ ์ œ์•ˆ ๋ฐฉ๋ฒ•์„ ํ”„๋กœํ† ํƒ€์ž… ์นฉ์„ ํ†ตํ•ด ๊ทธ ํšจ์šฉ์„ฑ์„ ๊ฒ€์ฆํ•˜๊ณ , ์ด์–ด์„œ ๋Šฅ๋™ ์†Œ์ž ๋ฐœ์ง„๊ธฐ๊ฐ€ ๋ฏธ๋ž˜์˜ ๊ณ ์† ์‹œ๋ฆฌ์–ผ ๋งํฌ์˜ ํด๋ฝํ‚น์— ์‚ฌ์šฉ๋  ๊ฐ€๋Šฅ์„ฑ์— ๋Œ€ํ•ด ๊ฒ€ํ† ํ•œ๋‹ค. ์ฒซ๋ฒˆ์งธ ์‹œ์—ฐ์œผ๋กœ์จ, ๊ณ ์ฃผํŒŒ ๊ณ ๋ฆฌ ๋ฐœ์ง„๊ธฐ์˜ ๋†’์€ ํ”Œ๋ฆฌ์ปค ์žก์Œ์„ ์™„ํ™”์‹œํ‚ค๊ธฐ ์œ„ํ•ด ๊ธฐ์ค€ ์‹ ํ˜ธ๋ฅผ ๋ฐฐ์ˆ˜ํ™”ํ•˜์—ฌ ๋’ท๋‹จ์˜ ์œ„์ƒ ๊ณ ์ • ๋ฃจํ”„์˜ ๋Œ€์—ญํญ์„ ํšจ๊ณผ์ ์œผ๋กœ ๊ทน๋Œ€ํ™” ์‹œํ‚ค๋Š” ํšŒ๋กœ ๊ธฐ์ˆ ์„ ์ œ์•ˆํ•œ๋‹ค. ๋ณธ ๊ธฐ์ˆ ์€ ์ง€ํ„ฐ๋ฅผ ๋ˆ„์  ์‹œํ‚ค์ง€ ์•Š์œผ๋ฉฐ ๋”ฐ๋ผ์„œ ๊นจ๋—ํ•œ ์ค‘๊ฐ„ ์ฃผํŒŒ์ˆ˜ ํด๋ฝ์„ ์ƒ์„ฑ์‹œ์ผœ ์œ„์ƒ ๊ณ ์ • ๋ฃจํ”„์™€ ํ•จ๊ป˜ ๋†’์€ ์„ฑ๋Šฅ์˜ ๊ณ ์ฃผํŒŒ ํด๋ฝ์„ ํ•ฉ์„ฑํ•œ๋‹ค. ๊ธฐ์ค€ ์‹ ํ˜ธ๋ฅผ ์„ฑ๊ณต์ ์œผ๋กœ ๋ฐฐ์ˆ˜ํ™”ํ•˜๊ธฐ ์œ„ํ•œ ํƒ€์ด๋ฐ ์กฐ๊ฑด๋“ค์„ ๋จผ์ € ๋ถ„์„ํ•˜์—ฌ ํƒ€์ด๋ฐ ์˜ค๋ฅ˜๋ฅผ ์ œ๊ฑฐํ•˜๊ธฐ ์œ„ํ•œ ๋ฐฉ๋ฒ•๋ก ์„ ํŒŒ์•…ํ•œ๋‹ค. ๊ฐ ๊ต์ • ์ค‘๋Ÿ‰์€ ์—ฐ์—ญ์  ํ™•๋ฅ ์„ ๊ธฐ๋ฐ˜์œผ๋กœํ•œ LMS ์•Œ๊ณ ๋ฆฌ์ฆ˜์„ ํ†ตํ•ด ๊ฐฑ์‹ ๋˜๋„๋ก ์„ค๊ณ„๋œ๋‹ค. ๊ต์ •์— ํ•„์š”ํ•œ ์‹œ๊ฐ„์„ ์ตœ์†Œํ™” ํ•˜๊ธฐ ์œ„ํ•˜์—ฌ, ๊ฐ ๊ต์ • ์ด๋“์€ ํƒ€์ด๋ฐ ์˜ค๋ฅ˜ ๊ทผ์›๋“ค์˜ ํฌ๊ธฐ๋ฅผ ๊ท€๋‚ฉ์ ์œผ๋กœ ์ถ”๋ก ํ•œ ๊ฐ’์„ ๋ฐ”ํƒ•์œผ๋กœ ์ง€์†์ ์œผ๋กœ ์ œ์–ด๋œ๋‹ค. 40-nm CMOS ๊ณต์ •์œผ๋กœ ๊ตฌํ˜„๋œ ํ”„๋กœํ† ํƒ€์ž… ์นฉ์˜ ์ธก์ •์„ ํ†ตํ•ด ์ €์†Œ์Œ, ๊ณ ์ฃผํŒŒ ํด๋ฝ์„ ๋น ๋ฅธ ๊ต์ • ์‹œ๊ฐ„์•ˆ์— ํ•ฉ์„ฑํ•ด ๋ƒ„์„ ํ™•์ธํ•˜์˜€๋‹ค. ์ด๋Š” 177/223 fs์˜ rms ์ง€ํ„ฐ๋ฅผ ๊ฐ€์ง€๋Š” 8/16 GHz์˜ ํด๋ฝ์„ ์ถœ๋ ฅํ•œ๋‹ค. ๋‘๋ฒˆ์งธ ์‹œ์—ฐ์œผ๋กœ์จ, ๊ณ ๋ฆฌ ๋ฐœ์ง„๊ธฐ์˜ ๋†’์€ ์ „์› ๋…ธ์ด์ฆˆ ์˜์กด์„ฑ์„ ์™„ํ™”์‹œํ‚ค๋Š” ๊ธฐ์ˆ ์ด ํฌํ•จ๋œ ์ฃผํŒŒ์ˆ˜ ํ•ฉ์„ฑ๊ธฐ๊ฐ€ ์„ค๊ณ„๋˜์—ˆ๋‹ค. ์ด๋Š” ๊ณ ๋ฆฌ ๋ฐœ์ง„๊ธฐ์˜ ์ „์•• ํ—ค๋“œ๋ฃธ์„ ๋ณด์กดํ•จ์œผ๋กœ์„œ ๊ณ ์ฃผํŒŒ ๋ฐœ์ง„์„ ๊ฐ€๋Šฅํ•˜๊ฒŒ ํ•œ๋‹ค. ๋‚˜์•„๊ฐ€, ์ „์› ๋…ธ์ด์ฆˆ ๊ฐ์†Œ ์„ฑ๋Šฅ์€ ๊ณต์ •, ์ „์••, ์˜จ๋„ ๋ณ€๋™์— ๋Œ€ํ•˜์—ฌ ๋ฏผ๊ฐํ•˜์ง€ ์•Š์œผ๋ฉฐ, ๋”ฐ๋ผ์„œ ์ถ”๊ฐ€์ ์ธ ๊ต์ • ํšŒ๋กœ๋ฅผ ํ•„์š”๋กœ ํ•˜์ง€ ์•Š๋Š”๋‹ค. ๋งˆ์ง€๋ง‰์œผ๋กœ, ์œ„์ƒ ๋…ธ์ด์ฆˆ์— ๋Œ€ํ•œ ํฌ๊ด„์  ๋ถ„์„๊ณผ ํšŒ๋กœ ์ตœ์ ํ™”๋ฅผ ํ†ตํ•˜์—ฌ ์ฃผํŒŒ์ˆ˜ ํ•ฉ์„ฑ๊ธฐ์˜ ์ €์žก์Œ ์ถœ๋ ฅ์„ ๋ฐฉํ•ดํ•˜์ง€ ์•Š๋Š” ๋ฐฉ๋ฒ•์„ ๊ณ ์•ˆํ•˜์˜€๋‹ค. ํ•ด๋‹น ํ”„๋กœํ† ํƒ€์ž… ์นฉ์€ 40-nm CMOS ๊ณต์ •์œผ๋กœ ๊ตฌํ˜„๋˜์—ˆ์œผ๋ฉฐ, ์ „์› ๋…ธ์ด์ฆˆ๊ฐ€ ์ธ๊ฐ€๋˜์ง€ ์•Š์€ ์ƒํƒœ์—์„œ 289 fs์˜ rms ์ง€ํ„ฐ๋ฅผ ๊ฐ€์ง€๋Š” 8 GHz์˜ ํด๋ฝ์„ ์ถœ๋ ฅํ•œ๋‹ค. ๋˜ํ•œ, 20 mVrms์˜ ์ „์› ๋…ธ์ด์ฆˆ๊ฐ€ ์ธ๊ฐ€๋˜์—ˆ์„ ๋•Œ์— ์œ ๋„๋˜๋Š” ์ง€ํ„ฐ์˜ ์–‘์„ -23.8 dB ๋งŒํผ ์ค„์ด๋Š” ๊ฒƒ์„ ํ™•์ธํ•˜์˜€๋‹ค.1 Introduction 1 1.1 Motivation 3 1.1.1 Clocking in High-Speed Serial Links 4 1.1.2 Multi-Phase, High-Frequency Clock Conversion 8 1.2 Dissertation Objectives 10 2 RO-Based High-Frequency Synthesis 12 2.1 Phase-Locked Loop Fundamentals 12 2.2 Toward All-Digital Regime 15 2.3 RO Design Challenges 21 2.3.1 Oscillator Phase Noise 21 2.3.2 Challenge 1: High Flicker Noise 23 2.3.3 Challenge 2: High Supply Noise Sensitivity 26 3 Filtering RO Noise 28 3.1 Introduction 28 3.2 Proposed Reference Octupler 34 3.2.1 Delay Constraint 34 3.2.2 Phase Error Calibration 38 3.2.3 Circuit Implementation 51 3.3 IL-ADPLL Implementation 55 3.4 Measurement Results 59 3.5 Summary 63 4 RO Supply Noise Compensation 69 4.1 Introduction 69 4.2 Proposed Analog Closed Loop for Supply Noise Compensation 72 4.2.1 Circuit Implementation 73 4.2.2 Frequency-Domain Analysis 76 4.2.3 Circuit Optimization 81 4.3 ADPLL Implementation 87 4.4 Measurement Results 90 4.5 Summary 98 5 Conclusions 99 A Notes on the 8REF 102 B Notes on the ACSC 105๋ฐ•

    A Two-stage approach to harmonic rejection mixing using blind interference cancelling

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    Current analog harmonic rejection mixers typically provide 30โ€“40 dB of harmonic rejection, which is often not sufficient. We present a mixed analog-digital approach to harmonic rejection mixing that uses a digital interference canceler to reject the strongest interferer. Simulations indicate that, given a practical RF scenario, the digital canceler is able to improve the signal-to-interference ratio by 30โ€“45 dB
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